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ltc6102 ltc6102-1/ltc6102hv 1 6102fe for more information www.linear.com/ltc6102 typical application features applications description precision zero drift current sense ampli?er the lt c ? 6102/ltc6102hv are versatile, high voltage, high- side current sense ampliiers. their high supply voltage rating allows their use in many high side applications, while the low drift and offset ensure accuracy across a wide range of operating conditions. the ltc6102-1 is a version of the ltc6102 that includes a low power disable mode to conserve system standby power. the ltc6102/ltc6102hv monitor current via the voltage across an external sense resistor (shunt resistor). internal circuitry converts input voltage to output current, allowing a small sense signal on a large common mode voltage to be translated to a ground-referred signal. low dc offset allows the use of very low shunt resistor values and large gain-setting resistors. as a result, power loss in the shunt is reduced. the wide operating supply and high accuracy make the ltc6102 ideal for a large array of applications, from auto - motive, to industrial and power management. a maximum input sense voltage of 2v allows a wide range of currents and voltages to be monitored. fast response makes the ltc6102 the perfect choice for load current warnings and shutoff protection control. all versions of the ltc6102 are available in 8-lead msop and 3mm 3mm dfn packages. n supply range: 4v to 60v, 70v maximum (ltc6102) 5v to 100v, 105v maximum (ltc6102hv) n 10v input offset maximum n 50nv/c input offset drift maximum n fast response: 1s step response n gain con?gurable with two resistors n low input bias current: 3na maximum n psrr 130db minimum n output currents up to 1ma n operating temperature range: C40c to 125c n disable mode (ltc6102-1 only): 1a maximum n available in 8-lead msop and 3mm 3mm dfn packages n current shunt measurement n battery monitoring n remote sensing n load protection n motor control n automotive controls dynamic current measurement range 10a current sense with 10ma resolution and 100mw maximum dissipation to p 6102 ta01 ltc2433-1 r out 4.99k v out 1f 5v l o a d v out = ? v sense = 249.5v sense r out r in *proper shunt selection could allowmonitoring of currents in excess of 1000a ltc6102 r in 20 v sense 1m 5v to 105v v + v C out +in +C Cinf Cins v reg 0.1f C + + dynamic range (db) maximum sense voltage (v) 0.0001 110100 9080 70 60 50 40 30 20 0.001 0.01 1 0.1 6102 ta01b dynamic range relative to 10v offset voltage r sense = 100m max v sense = 1v r sense = 10m max v sense = 100v l , lt, ltc, ltm, linear technology and the linear logo are registered trademarks of linear technology corporation. all other trademarks are the property of their respective owners. downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 2 6102fe for more information www.linear.com/ltc6102 absolute maximum ratings total supply voltage (v + to v C ): ltc6102/ltc6102-1 ............................................. 70v ltc6102hv ......................................................... 105v input voltage range Cinf, Cins ................................ (v + C 4v to v + + 0.3v) +in ............................................ (v + C 20v to v + + 1v) en ............................................ (v C C 0.3v to v C + 9v) differential (Cins C +in), 1 second ...................... 60v output voltage range ltc6102/ltc6102hv ............... (v C C 0.3v to v C + 9v) ltc6102-1 ............................. (v C C 0.3v to v C + 15v) input current Cinf, Cins ........................................................ 10ma +in ................................................................... C10ma en .................................................................... 10ma (note 1) output current ....................................... (C1ma, +10ma) output short circuit duration........................... indeinite operating temperature range: (note 2) ltc6102c/ltc6102c-1/ltc6102hvc .. C40c to 85c ltc6102i/ltc6102i-1/ltc6102hvi ...... C40c to 85c ltc6102h/ltc6102h-1 ltc6102hvh ...................................... C40c to 125c speciied temperature range: (note 2) ltc6102c/ltc6102c-1/ltc6102hvc ...... 0c to 70c ltc6102i/ltc6102i-1/ltc6102hvi ...... C40c to 85c ltc6102h/ltc6102h-1 ltc6102hvh ...................................... C40c to 125c storage temperature range ................... C65c to 150c top view dd package 8-lead (3mm 3mm) plastic dfn 5 6 7 8 4 9 3 2 1 Cins Cinf v C /en* out +inv + v reg v C t jmax = 150c, ja = 43c/w exposed pad (pin 9) is v C , must be soldered to pcb *v C for the ltc6102/ltc6102hv, en for the ltc6102-1 12 3 4 Cins Cinf v C /en* out 87 6 5 +inv + v reg v C top view ms8 package 8-lead plastic msop t jmax = 150c, ja = 200c/w *v C for the ltc6102/ltc6102hv, en for the ltc6102-1 pin configuration lead free finish tape and reel part marking* package description specified temperature range ltc6102cdd#pbf ltc6102cdd#trpbf lckh 8-lead (3mm 3mm) plastic dfn 0c to 70c ltc6102idd#pbf ltc6102idd#trpbf lckh 8-lead (3mm 3mm) plastic dfn C40c to 85c ltc6102hdd#pbf ltc6102hdd#trpbf lckh 8-lead (3mm 3mm) plastic dfn C40c to 125c ltc6102cdd-1#pbf ltc6102cdd-1#trpbf ldyb 8-lead (3mm 3mm) plastic dfn 0c to 70c ltc6102idd-1#pbf ltc6102idd-1#trpbf ldyb 8-lead (3mm 3mm) plastic dfn C40c to 85c ltc6102hdd-1#pbf ltc6102hdd-1#trpbf ldyb 8-lead (3mm 3mm) plastic dfn C40c to 125c ltc6102hvcdd#pbf ltc6102hvcdd#trpbf lcvc 8-lead (3mm 3mm) plastic dfn 0c to 70c ltc6102hvidd#pbf ltc6102hvidd#trpbf lcvc 8-lead (3mm 3mm) plastic dfn C40c to 85c ltc6102hvhdd#pbf ltc6102hvhdd#trpbf lcvc 8-lead (3mm 3mm) plastic dfn C40c to 125c ltc6102cms8#pbf ltc6102cms8#trpbf ltckj 8-lead plastic msop 0c to 70c ltc6102ims8#pbf ltc6102ims8#trpbf ltckj 8-lead plastic msop C40c to 85c order information downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 3 6102fe for more information www.linear.com/ltc6102 order information lead free finish tape and reel part marking* package description specified temperature range ltc6102hms8#pbf ltc6102hms8#trpbf ltckj 8-lead plastic msop C40c to 125c ltc6102cms8-1#pbf ltc6102cms8-1#trpbf ltdxz 8-lead plastic msop 0c to 70c ltc6102ims8-1#pbf ltc6102ims8-1#trpbf ltdxz 8-lead plastic msop C40c to 85c ltc6102hms8-1#pbf ltc6102hms8-1#trpbf ltdxz 8-lead plastic msop C40c to 125c ltc6102hvcms8#pbf ltc6102hvcms8#trpbf ltcvb 8-lead plastic msop 0c to 70c ltc6102hvims8#pbf ltc6102hvims8#trpbf ltcvb 8-lead plastic msop C40c to 85c LTC6102HVHMS8#pbf LTC6102HVHMS8#trpbf ltcvb 8-lead plastic msop C40c to 125c lead based finish tape and reel part marking* package description specified temperature range ltc6102cdd ltc6102cdd#tr lckh 8-lead (3mm 3mm) plastic dfn 0c to 70c ltc6102idd ltc6102idd#tr lckh 8-lead (3mm 3mm) plastic dfn C40c to 85c ltc6102hdd ltc6102hdd#tr lckh 8-lead (3mm 3mm) plastic dfn C40c to 125c ltc6102cdd-1 ltc6102cdd-1#tr ldyb 8-lead (3mm 3mm) plastic dfn 0c to 70c ltc6102idd-1 ltc6102idd-1#tr ldyb 8-lead (3mm 3mm) plastic dfn C40c to 85c ltc6102hdd-1 ltc6102hdd-1#tr ldyb 8-lead (3mm 3mm) plastic dfn C40c to 125c ltc6102hvcdd ltc6102hvcdd#tr lcvc 8-lead (3mm 3mm) plastic dfn 0c to 70c ltc6102hvidd ltc6102hvidd#tr lcvc 8-lead (3mm 3mm) plastic dfn C40c to 85c ltc6102hvhdd ltc6102hvhdd#tr lcvc 8-lead (3mm 3mm) plastic dfn C40c to 125c ltc6102cms8 ltc6102cms8#tr ltckj 8-lead plastic msop 0c to 70c ltc6102ims8 ltc6102ims8#tr ltckj 8-lead plastic msop C40c to 85c ltc6102hms8 ltc6102hms8#tr ltckj 8-lead plastic msop C40c to 125c ltc6102cms8-1 ltc6102cms8-1#tr ltdxz 8-lead plastic msop 0c to 70c ltc6102ims8-1 ltc6102ims8-1#tr ltdxz 8-lead plastic msop C40c to 85c ltc6102hms8-1 ltc6102hms8-1#tr ltdxz 8-lead plastic msop C40c to 125c ltc6102hvcms8 ltc6102hvcms8#tr ltcvb 8-lead plastic msop 0c to 70c ltc6102hvims8 ltc6102hvims8#tr ltcvb 8-lead plastic msop C40c to 85c LTC6102HVHMS8 LTC6102HVHMS8#tr ltcvb 8-lead plastic msop C40c to 125c consult ltc marketing for parts speciied with wider operating temperature ranges. *the temperature grade is identiied by a label on the shipping container. for more information on lead free part marking, go to: http://www.linear.com/leadfree/ for more information on tape and reel speciications, go to: http://www.linear.com/tapeandreel/ downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 4 6102fe for more information www.linear.com/ltc6102 electrical characteristics (ltc6102, ltc6102-1) the l denotes the speci?cations which apply over the full operating temperature range, otherwise speci?cations are at t a = 25c. r in = 10 , r out = 10k, v sense + = v + (see figure 1 for details), v + = 12v, v ? = 0v, v en = 2.2v unless otherwise noted. symbol parameter conditions min typ max units v + supply voltage range 4 60 v v os input offset voltage (note 3) v sense = 100v 6v v + 60v v + = 4v 3 5 10 25 v v input offset voltage (note 4) v sense = 100v 6v v + 60v v + = 4v 3 5 35 50 v v v os / t input offset voltage drift (note 3) v sense = 100v ltc6102c, ltc6102i, ltc6102c-1, ltc6102i-1 ltc6102h, ltc6102h-1 l l 25 25 50 75 nv/c nv/c i b input bias current (note 5) r in = 40k, v sense = 2mv ltc6102c, ltc6102i, ltc6102c-1, ltc6102i-1 ltc6102h, ltc6102h-1 l l 60 3 20 pa na na psrr power supply rejection ratio v sense = 100v, v + = 6v to 60v l 130 125 150 db db v sense = 100v, v + = 4v to 60v l 120 115 140 db db v sense(max) input sense voltage full scale (v + C v in + ) error <1%, r in = 10k, r out = 10k 6v v + 60v v + = 4v l l 2 0.8 v v v out maximum output voltage (ltc6102) v sense = 2mv, r out = 100k 12v v + 60v v + = 6v v + = 4v l l l 8 3 1 v v v maximum output voltage (l tc6102-1) v sense = 2mv, r out = 100k v + = 60v v + = 12v v + = 4v l l l 14 11.7 3.8 v v v i out maximum output current 6v v + 60v, r in = 1k, r out = 1k, v sense = 1.1v v + = 4v, r in = 10, r out = 1k, v sense = 11mv l l 1 0.5 ma ma t r input step response (to 2.5v on a 5v output step) v sense = 100mv transient, 6v v + 60v, r in = 100, r out = 4.99k, i out = 100a 1 s v + = 4v 1.5 s bw signal bandwidth i out = 200a, r in = 100, r out = 4.99k i out = 1ma, r in = 100, r out = 4.99k 140 200 khz khz e n input noise voltage 0.1hz to 10hz 2 v p-p i s supply current v + = 4v, i out = 0, r in = 10k, r out = 100k l 275 400 475 a a v + = 6v, i out = 0, r in = 10k, r out = 100k l 290 425 500 a a v + = 12v, i out = 0, r in = 10k, r out = 100k l 300 450 525 a a v + = 60v, i out = 0, r in = 10k, r out = 100k 420 575 a ltc6102c, ltc6102i, ltc6102c-1, ltc6102i-1 l 650 a ltc6102h, ltc6102h-1 l 675 a i dis supply current in disable mode (ltc6102-1 only) v en = 0.8v, v + = 12v v en = 0.8v, v + = 60v l l 1 18 a a v enl enable input voltage low (ltc6102-1 only) l 0.8 v downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 5 6102fe for more information www.linear.com/ltc6102 electrical characteristics (ltc6102hv) the l denotes the speci?cations which apply over the full operating temperature range, otherwise speci?cations are at t a = 25c. r in = 10 , r out = 10k, v sense + = v + (see figure 1 for details), v + = 12v, v ? = 0v unless otherwise noted. symbol parameter conditions min typ max units v + supply voltage range 5 100 v v os input offset voltage (note 3) v sense = 100v 6v v + 100v v + = 5v 3 5 10 25 v v input offset voltage (note 4) v sense = 100v 6v v + 100v v + = 5v 3 5 35 50 v v v os / t input offset voltage drift (note 3) v sense = 100v ltc6102hvc, ltc6102hvi ltc6102hvh l l 25 25 50 75 nv/c nv/c i b input bias current (note 5) r in = 40k, v sense = 2mv ltc6102hvc, ltc6102hvi ltc6102hvh l l 60 3 20 pa na na psrr power supply rejection ratio v sense = 100v, v + = 6v to 100v l 130 125 150 db db v sense = 100v, v + = 5v to 100v l 120 115 140 db db v sense(max) input sense voltage full scale (v + C v +in ) error <1%, r in = 10k, r out = 10k 6v v + 100v v + = 5v l l 2 1 v v v out maximum output voltage v sense = 2mv, r out = 100k 12v v + 100v v + = 5v l l 8 3 v v i out maximum output current 6v v + 100v, r in = 1k, r out = 1k, v sense = 1.1v v + = 5v, r in = 10, r out = 1k, v sense = 11mv l l 1 0.5 ma ma t r input step response (to 2.5v on a 5v output step) v sense = 100mv transient, 6v v + 100v, r in = 100, r out = 4.99k, i out = 100a 1 s v + = 5v 1.5 s bw signal bandwidth i out = 200a, r in = 100, r out = 4.99k i out = 1ma, r in = 100, r out = 4.99k 140 200 khz khz e n input noise voltage 0.1hz to 10hz 2 v p-p symbol parameter conditions min typ max units v enh enable input voltage high (ltc6102-1 only) l 2.2 v i ben enable input pin current (ltc6102-1 only) v en = 0v to 9v l 8 a t on turn-on time (ltc6102-1 only) v en = 2.2v, v sense = 1mv, output settles to within 1% of final value 500 s t off turn-off time (ltc6102-1 only) v en = 0.8v, v sense = 1mv, supply current drops to less than 10% of nominal value 100 s f s sampling frequency 10 khz (ltc6102, ltc6102-1) the l denotes the speci?cations which apply over the full operating temperature range, otherwise speci?cations are at t a = 25c. r in = 10 , r out = 10k, v sense + = v + (see figure 1 for details), v + = 12v, v ? = 0v, v en = 2.2v unless otherwise noted. electrical characteristics downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 6 6102fe for more information www.linear.com/ltc6102 note 1: stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. exposure to any absolute maximum rating condition for extended periods may affect device reliability and lifetime. in addition to the absolute maximum ratings, the output current of the ltc6102 must be limited to ensure that the power dissipation in the ltc6102 does not allow the die temperature to exceed 150c. see the applications information output current limitations due to power dissipation for further information. note 2: the ltc6102c/ltc6102c-1/ltc6102hvc are guaranteed to meet speciied performance from 0c to 70c. the ltc6102c/ltc6102c-1/ ltc6102hvc are designed, characterized and expected to meet speciied performance from C40c to 85c but are not tested or qa sampled at these temperatures. ltc6102i/ltc6102i-1/ltc6102hvi are guaranteed to meet speciied performance from C40c to 85c. the ltc6102h/ ltc6102h-1/ltc6102hvh are guaranteed to meet speciied performance from C40c to 125c. note 3: these parameters are guaranteed by design and are not 100% tested. thermocouple effects preclude measurements of these voltage levels during automated testing. note 4: limits are fully tested. limit is determined by high speed automated test capability. note 5: i b speciication is limited by practical automated test resolution. please refer to the typical performance characteristics section for more information regarding actual typical performance. for tighter speciications, please contact ltc marketing. (ltc6102hv) the l denotes the speci?cations which apply over the full operating temperature range, otherwise speci?cations are at t a = 25c. r in = 10 , r out = 10k, v sense + = v + (see figure 1 for details), v + = 12v, v ? = 0v unless otherwise noted. electrical characteristics symbol parameter conditions min typ max units i s supply current v + = 5v, i out = 0, r in = 10k, r out = 100k l 275 400 475 a a v + = 6v, i out = 0, r in = 10k, r out = 100k l 280 425 500 a a v + = 12v, i out = 0, r in = 10k, r out = 100k l 290 450 525 a a v + = 100v, i out = 0, r in = 10k, r out = 100k 420 575 a ltc6102hvc, ltc6102hvi l 650 a ltc6102hvh l 675 a f s sampling frequency 10 khz downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 7 6102fe for more information www.linear.com/ltc6102 input v os vs temperature input v os vs supply voltage input sense range ltc6102: v out maximum vs temperature ltc6102hv: v out maximum vs temperature ltc6102/ltc6102-1: i out maximum vs temperature input offset ( v) 20 1510 50 C5 C10C15 C20 6102 g01 temperature ( c) C40 120 0 40 80 C20 20 60 100 v s = 12v v s = 4v supply voltage (v) 6102 g02 4 32 12 16 8 24 28 20 36 44 48 40 52 56 60 input offset ( v) 20 1510 50 C5 C10C15 C20 t a = C40 c t a = 0 c t a = 25 c t a = 70 c t a = 85 c t a = 125 c 0 40 20 120 100 60 80 v supply (v) maximum v sense (v) 3.0 2.52.0 1.5 1.0 0.5 0 6102 g03 t a = 25 c temperature ( c) C40 40 80 120 100 C20 6102 g04 0 20 60 maximum v out (v) v s = 60v v s = 12v v s = 6v v s = 5v v s = 4v 15 1413 12 11 10 98 7 6 5 4 3 2 1 0 temperature ( c) C40 40 80 120 100 C20 6102 g05 0 20 60 maximum v out (v) v s = 100v v s = 12v v s = 6v v s = 5v 15 1413 12 11 10 98 7 6 5 4 3 2 1 0 temperature ( c) 6102 g06 maximum i out (ma) v s = 12v v s = 60v v s = 6v v s = 5v v s = 4v C40 40 80 120 100 C20 0 20 60 6.5 6.05.5 5.0 4.5 4.0 3.5 3.0 2.5 2.0 1.5 1.0 0.5 0 typical performance characteristics ltc6102hv: i out maximum vs temperature gain vs frequency temperature ( c) 6102 g07 maximum i out (ma) v s = 12v v s = 100v v s = 6v v s = 5v C40 40 80 120 100 C20 0 20 60 6.56.0 5.5 5.0 4.5 4.0 3.5 3.0 2.5 2.0 1.5 1.0 0.5 0 gain (db) frequency (hz) 1k 40 3530 25 20 15 10 50 C5 C10 10k 100k 10m 1m 6102 g09 t a = 25 c v + = 12v r in = 100 r out = 4.99k i out = 200 a dc i out = 1ma dc input bias current vs temperature 100000 10 100 1000 10000 temperature ( c) C40 40 80 120 100 C20 6102 g10 0 20 60 bias current (pa) v s = 100v v s = 60v v s = 12v v s = 6v v s = 5v downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 8 6102fe for more information www.linear.com/ltc6102 typical performance characteristics ltc6102: supply current vs supply voltage step response 0mv to 10mv step response 10mv to 20mv ltc6102hv: supply current vs supply voltage step response 100mv 600500 400 300 200 100 0 supply voltage (v) 0 supply current ( a) 32 6102 g11 8 16 48 56 24 40 28 4 12 44 52 20 36 60 v in = 0 r in = 2m t a = 125 c t a = 85 c t a = 70 c t a = 25 c t a = C40 c t a = 0 c 600500 400 300 200 100 0 supply voltage (v) 0 supply current ( a) 32 6102 g12 8 16 48 56 64 72 80 88 96 24 40 v in = 0 r in = 2m t a = 125 c t a = C40 c t a = 70 c t a = 85 c t a = 25 c t a = 0 c v + v + C 10mv 0.5v 0v time (10 s/div) 6102 g13 t a = 25 c v + = 12v r in = 100 r out = 4.99k v sense + = v + v sense C v out v + C 10mv v + C 20mv 1v 0.5v 6102 g14 time (10 s/div) t a = 25 c v + = 12v r in = 100 r out = 4.99k v sense + = v + v sense C v out v + v + C 100mv 5v0v 6102 g15 c load = 1000pf c load = 10pf time (10 s/div) t a = 25 c v + = 12v r in = 100 r out = 4.99k v sense + = v + v sense C v out step response rising edge 5.5v 5v 0.5v 0v time (500ns/div) 6102 g17 v out v sense C = 100mv i out = 100 a i out = 0 t a = 25 c v + = 12v r in = 100 r out = 4.99k v sense + = v + step response falling edge psrr vs frequency 5.5v 5v 0.5v 0v 6102 g18 v out v sense C = 100mv i out = 100 a i out = 0 time (500ns/div) t a = 25 c v + = 12v r in = 100 r out = 4.99k v sense + = v + frequency (hz) psrr (db) 0.1 1 10 100 1k 10k 100k 1m 6102 g19 160 140120 100 8060 40 20 v + = 12v r in = 100 r out = 4.99k a v = 49.9 i out = 500 a input referred noise 0.1hz to 10hz 6102 g20 t a = 25 c v + = 12v r in = 10 r out = 1k v sense = 2mv time (s) noise ( v) 0 1 2 3 4 5 6 7 8 9 10 54 3 2 1 0 C5 C4 C3 C2 C1 downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 9 6102fe for more information www.linear.com/ltc6102 typical performance characteristics noise spectral density voltage noise density (nv/ hz) frequency (hz) 100 200 100 0 1k 10k 1m 100k 6102 g21 gain = 10 ltc6102-1: supply current vs supply voltage ltc6102-1: supply current vs supply voltage when disabled ltc6102-1: supply current vs enable voltage ltc6102-1: enable pin current vs enable voltage voltage supply (v) 0 300 400 600 30 50 6102 g22 200100 10 20 40 60 70 0 C100 500 supply current (a) v en = 2v v sense = C0.1v t a = 125c t a = C40c t a = 85c t a = 25c supply voltage (v) 0 supply current (a) 10 14 18 40 6102 g23 6 2 8 12 16 4 0 C2 10 20 30 50 70 60 t a = 125c t a = C40c t a = 25c t a = 85c v en = 0.8v enable voltage (v) 0 supply current (a) 250 350 450 8 6102 g24 150 50 200 300 400100 0 ?50 2 1 4 3 6 7 9 5 10 t a = 25c v sense = 0v v + = 60v v + = 12v turn off (12v) enable voltage (v) 0 0 C1 enable pin current (a) 1 3 4 5 1 5 7 6102 g25 2 6 4 9 10 2 3 6 8 t a = 25c v + = 12v ltc6102-1: turn-on time ltc6102-1: turn-off time time (s) C200 C1 voltage (v) 0 2 3 4 400 600 8 6102 g26 1 0 200 800 en 5 6 7 out t a = 25c v + = 12v v sense = 1mv time (s) C20 C0.5 voltage (v) 0 1.0 1.5 2.0 10 20 4.0 6102 g27 0.5 C10 0 C15 15 25 C5 5 30 2.5 3.0 3.5 out t a = 25c v + = 12v v sense = 1mv en downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 10 6102fe for more information www.linear.com/ltc6102 ?ins (pin 1): ampliier inverting input. when tied to Cinf, the internal sense ampliier will drive Cins to the same potential as +in. ?inf (pin 2): force input. this pin carries the input current from r in and must be tied to Cins near r in . a resistor (r in ) tied from v + to Cinf sets the output current i out = v sense /r in . v sense is the voltage across the ex - ternal r sense . v ? (pin 3, ltc6102/ltc6102hv only): negative supply. en (pin 3, ltc6102-1 only): enable pin, referenced to the negative supply. when the enable pin is pulled high, the ltc6102-1 is active. when the enable pin is pulled low or left loating, the ltc6102-1 is disabled. out (pin 4): open-drain current output. out will source a current that is proportional to the sense voltage into an external resistor. i out is the same current that enters Cinf. v ? (pin 5): negative supply. v reg (pin 6): internal regulated supply. a 0.1f (or larger) capacitor should be tied from v reg to v + . v reg is not designed to drive external circuits. v + (pin 7): positive supply. supply current is drawn through this pin.+in (pin 8): ampliier noninverting input. must be tied to the system load end of the sense resistor. the +in pin has an internal 5k series resistor designed to allow large input voltage transients or accidental disconnection of the sense resistor. this pin can be held up to 20v below the Cins pin indeinitely, or up to 60v below the Cins pin for up to one second (see absolute maximum ratings). exposed pad (pin 9, dfn only): v C . the exposed pad must be soldered to pcb. pin functions downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 11 6102fe for more information www.linear.com/ltc6102 block diagram figure 1. block diagram and typical connection C + v + v reg 0.1f v C v C en* v enable out *ltc6102-1 only 6102 bd i out r out r in r sense v sense i load v battery l o a d v out = v sense ? r out r in 5k 5k 10v 5v 10v 5v Cins Cinf +in +C downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 12 6102fe for more information www.linear.com/ltc6102 the ltc6102 high side current sense ampliier (figure 1) provides accurate monitoring of current through a user- selected sense resistor. the sense voltage is ampliied by a user-selected gain and level shifted from the positive power supply to a ground-referred output. the output signal is analog and may be used as is or processed with an output ilter. theory of operation an internal sense ampliier loop forces Cins to have the same potential as +in. connecting an external resistor, r in , between Cins and v + forces a potential across r in that is the same as the sense voltage across r sense . a corresponding current, v sense /r in , will low through r in . the high impedance inputs of the sense ampliier will not conduct this input current, so it will low through the Cinf pin and an internal mosfet to the output pin. the output current can be transformed into a voltage by adding a resistor from out to v C . the output voltage is then v o = v C + i out ? r out . useful gain con?gurations gain r in r out v sense at v out = 5v 200 49.9 10k 25mv 500 20 10k 10mv 1000 10 10k 5mv 4990 1 4.99k 1mv selection of external current sense resistor the external sense resistor, r sense , has a signiicant effect on the function of a current sensing system and must be chosen with care. first, the power dissipation in the resistor should be considered. the system load current will cause both heat dissipation and voltage loss in r sense . as a result, the sense resistor should be as small as possible while still providing the input dynamic range required by the measurement. note that input dynamic range is the difference between the maximum input signal and the minimum accurately reproduced signal, and is limited primarily by input dc offset of the internal ampliier of the ltc6102. in addition, r sense must be small enough that v sense does not exceed applications information the maximum sense voltage speciied by the ltc6102 or the sense resistor, even under peak load conditions. as an example, an application may require that the maximum sense voltage be 100mv. if this application is expected to draw 20a at peak load, r sense should be no more than 5m.once the maximum r sense value is determined, the minimum sense resistor value will be set by the resolu - tion or dynamic range required. the minimum signal that can be accurately represented by this sense amp is limited by the input offset. as an example, the ltc6102 has a typical input offset of 3v. if the minimum current is 1ma, a sense resistor of 3m will set v sense to 3v. this is the same value as the input offset. a larger sense resistor will reduce the error due to offset by increasing the sense voltage for a given load current. for this example, choosing a 5m r sense will maximize the dynamic range and provide a system that has 100mv across the sense resistor at peak load (20a), while input offset causes an error equivalent to only 0.6ma of load current. peak dissipation is 2w. if a 0.5m sense resistor is em - ployed, then the effective current error is 6ma (0.03% of full-scale), while the peak sense voltage is reduced to 10mv at 20a, dissipating only 200mw. the low offset and corresponding large dynamic range of the ltc6102 make it more lexible than other solutions in this respect. the 3v typical offset gives 100db of dy - namic range for a sense voltage that is limited to 300mv max, and over 116db of dynamic range if a maximum of 2v is allowed. the previous example assumes that a large output dynamic range is required. for circuits that do not require large dynamic range, the wide input range of the ltc6102 may be used to reduce the size of the sense resistor, reducing power loss and increasing reliability. for example, in a 100a circuit requiring 60db of dynamic range, the input offset and drift of most current-sense solutions will require that the shunt be chosen so that the sense voltage is at least 100mv at full scale so that the minimum input is greater than 100v. this will cause power dissipation in excess of 10w at full scale! that much power loss can put downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 13 6102fe for more information www.linear.com/ltc6102 dynamic range vs maximum power dissipation in r sense applications information a signiicant load on the power supply and create thermal design headaches. in addition, heating in the sense resistor can reduce its accuracy and reliability. in contrast, the large dynamic range of the ltc6102 allows the use of a much smaller sense resistor. the ltc6102 allows the minimum sense voltage to be reduced to less than 10v. the peak sense voltage would then be 10mv, dissipating only 1w at 100a in a 100? sense resistor! with a specialized sense resistor, the same system would allow peak currents of more than 1000a without exceeding the input range of the ltc6102 or damaging the shunt. figure 2. kelvin input connection preserves accuracy with large load current and large output current ltc6102 r out v out 6102 f02 r in C v + load r sense r in + C + v + Cinf v C out v reg 0.1f tie as close to r in as possible Cins +in load v + v C output r sense * r out ltc6102 r in C r in + c reg *vishay vcs1625 series with 4 pad kelvin connection v C high-current paths, this error can be reduced by orders of magnitude. a sense resistor with integrated kelvin sense terminals will give the best results. figure 2 illustrates the recommended method. note that the ltc6102 has a kelvin input structure such that current lows into Cinf. the Cins and Cinf pins should be tied as close as possible to r in . this reduces the parasitic series resistance so that r in may be as low as 1, allowing high gain settings to be used with very little gain error. sense resistor connectionkelvin connection of +in and Cins to the sense resistor should be used in all but the lowest power applications. solder connections and pc board interconnections that carry high current can cause signiicant error in measure - ment due to their relatively large resistances. one 10mm 10mm square trace of one-ounce copper is approxi - mately 0.5m. a 1mv error can be caused by as little as 2a lowing through this small interconnect. this will cause a 1% error in a 100mv signal. a 10a load current in the same interconnect will cause a 5% error for the same 100mv signal. an additional error is caused by the change in copper resistance over temperature, which is in excess of 0.4%/c. by isolating the sense traces from the selection of external input resistor, r in the external input resistor, r in , controls the transconduc - tance of the current sense circuit, i out = v sense /r in . for example, if r in = 100, then i out = v sense /100 or i out = 1ma for v sense = 100mv. r in should be chosen to provide the required resolution while limiting the output current. at low supply voltage, i out may be as much as 1ma. by setting r in such that maximum power dissipation (w) dynamic range (db) 110100 9080 70 60 50 40 30 20 6102 ai01 0.001 0.01 0.1 1 10 100 max i sense = 1a max i sense = 10a max i sense = 100a dynamic range relative to 10v, minimum v sense r sense = 10m r sense = 100m 100db: maxv sense = 1v 40db: maxv sense = 1mv r sense = 10? r sense = 100? r sense = 1 r sense = 1m downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 14 6102fe for more information www.linear.com/ltc6102 the largest expected sense voltage gives i out = 1ma, then the maximum output dynamic range is available. output dynamic range is limited by both the maximum allowed output current (note 1) and the maximum allowed output voltage, as well as the minimum practical output signal. if less dynamic range is required, then r in can be increased accordingly, reducing the output current and power dis - sipation. if small sense currents must be resolved ac - curately in a system that has very wide dynamic range, a smaller r in may be used if the max current is limited in another way, such as with a schottky diode across r sense (figure 3). this will reduce the high current measurement accuracy by limiting the result, while increasing the low current measurement resolution. this approach can be helpful in cases where occasional large burst currents may be ignored. applications information the ltc6102, and into r out via the out pin. in order to minimize gain error, Cins should be routed in a separate path from Cinf to a point as close to r in as possible. in addition, the higher potential terminal of r in should be connected directly to the positive terminal of r sense (or any input voltage source). for the highest accuracy, r in should be a four-terminal resistor if it is less than 10. selection of external output resistor, r out the output resistor, r out , determines how the output cur - rent is converted to voltage. v out is simply i out ? r out . in choosing an output resistor, the max output voltage must irst be considered. if the circuit that is driven by the output does not have a limited input voltage, then r out must be chosen such that the max output voltage does not exceed the ltc6102 max output voltage rating. if the following circuit is a buffer or adc with limited input range, then r out must be chosen so that i out(max) ? r out is less than the allowed maximum input range of this circuit. in addition, the output impedance is determined by r out . if the circuit to be driven has high enough input impedance, then almost any output impedance will be acceptable. however, if the driven circuit has relatively low input imped - ance, or draws spikes of current, such as an adc might do, then a lower r out value may be required in order to preserve the accuracy of the output. as an example, if the input impedance of the driven circuit is 100 times r out , then the accuracy of v out will be reduced by 1% since: vi rr rr out out out in dri ve n out in dri ve n = + = ? ? () () i ir ir out out out out ?? .? ? 100 101 09 9 = error sourcesthe current sense system uses an ampliier and resistors to apply gain and level shift the result. the output is then dependent on the characteristics of the ampliier, such as gain and input offset, as well as resistor matching. figure 3. shunt diode limits maximum input voltage to allow better low input resolution without overranging v + load d sense 6102 f03 r sense care should be taken when designing the pc board lay - out for r in , especially for small r in values. all trace and interconnect impedances will increase the effective r in value, causing a gain error. it is important to note that the large temperature drift of copper resistance will cause a change in gain over temperature if proper care is not taken to reduce this effect. to further limit the effect of trace resistance on gain, maximizing the accuracy of these circuits, the ltc6102 has been designed with a kelvin input. the inverting terminal (Cins) is separate from the feedback path (Cinf). during operation, these two pins must be connected together. the design of the ltc6102 is such that current into Cins is input bias current only, which is typically 60pa at 25c. almost all of the current from r in lows into Cinf, through downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 15 6102fe for more information www.linear.com/ltc6102 figure 5. second input r minimizes error due to input bias current Cinf v reg 0.1f Cins 6102 f05 r in + = r in C C r sense ltc6102 r out v out v + load r sense C + v + v C out +in r in C r in + applications information for instance if i bias is 1na and r out is 10k, the output error is C10v. note that in applications where r sense r in , i b (+) causes a voltage offset in r sense that cancels the error due to i b (C) and e out(ibias) 0. in applications where r sense < r in , the bias current error can be similarly reduced if an external resistor r in (+) = (r in C r sense ) is connected as shown in figure 5. under both conditions: e out(ibias) = r out ? i os ; i os = i b (+) C i b (C) adding r in + as described will maximize the dynamic range of the circuit. for less sensitive designs, r in + is not necessary. ideally, the circuit output is: vv r r vr i out se ns e out in se ns es en se se ns e == ?; ? in this case, the only error is due to resistor mismatch, which provides an error in gain only. output error, e out , due to the ampli?er dc offset voltage, v os e out(vos) = v os ? (r out /r in ) the dc offset voltage of the ampliier adds directly to the value of the sense voltage, v sense . this error is very small (3v typ) and may be ignored for reasonable values of r in . see figure 4. for very high dynamic range, this offset can be calibrated in the system due to its extremely low drift. input voltage (v) output error (%) 100 10 1 0.1 0.01 0.001 0.0001 6102 f04 0.00001 0.0001 0.001 0.01 0.1 1 for a 500 ? shunt v in = 100mv, i shunt = 200a error due to v os is 6ma v in = 10 v figure 4. ltc6102 output error due to typical input offset vs input voltage output error, e out , due to the bias currents, i b (+) and i b (?) the input bias current of the ltc6102 is vanishingly small. however, for very high resolution, or at high temperatures where i b increases due to leakage, the current may be signiicant.the bias current i b (+) lows into the positive input of the internal op amp. i b (C) lows into the negative input. e out(ibias) = r out ((i b (+) ? (r sense /r in ) C i b (C)) since i b (+) i b (C) = i bias , if r sense << r in then, e out(ibias) Cr out ? i bias clock feedthrough, input bias current the ltc6102 uses auto-zeroing circuitry to achieve an almost zero dc offset over temperature, sense voltage, and power supply voltage. the frequency of the clock used for auto-zeroing is typically 10khz. the term clock feedthrough is broadly used to indicate visibility of this clock frequency in the op amp output spectrum. there are typically two types of clock feedthrough in auto zeroed amps like the ltc6102. the irst form of clock feedthrough is caused by the settling of the internal sampling capacitor and is input referred; that is, it is multiplied by the internal loop gain downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 16 6102fe for more information www.linear.com/ltc6102 of the amp. this form of clock feedthrough is indepen - dent of the magnitude of the input source resistance or the magnitude of the gain setting resistors. the ltc6102 has a residue clock feedthrough of less then 1 v rms input referred at 10khz.the second form of clock feedthrough is caused by the small amount of charge injection occurring during the sampling and holding of the amps input offset voltage. the current spikes are multiplied by the impedance seen at the input terminals of the amp, appearing at the output multiplied by the internal loop gain of the internal op amp. to reduce this form of clock feedthrough, use smaller valued gain setting resistors and minimize the source resistance at the input. input bias current is deined as the dc current into the input pins of the op amp. the same current spikes that cause the second form of clock feedthrough described above, when averaged, dominate the dc input bias current of the op amp below 70c. as temperature increases, the leakage of the esd protec - tion diodes on the inputs increases the input bias currents of both inputs in the positive direction, while the current caused by the charge injection stays relatively constant. at temperatures above 70c, the leakage current dominates and both the negative and positive pins input bias currents are in the positive direction (into the pins). output current limitations due to power dissipation the l tc6102 can deliver more than 1ma continuous cur - rent to the output pin. this current lows through r in and enters the current sense amp via the Cinf pin. the power dissipated in the ltc6102 due to the output current is: p out = (v Cinf C v out ) ? i out since v Cinf v + , p out (v + C v out ) ? i out there is also power dissipated due to the quiescent sup - ply current: p q = i s ? v + the total power dissipated is the output current dissipation plus the quiescent dissipation: p total = p out + p q applications information at maximum supply and maximum output current, the total power dissipation can exceed 100mw. this will cause signiicant heating of the ltc6102 die. in order to prevent damage to the ltc6102, the maximum expected dissipation in each application should be calculated. this number can be multiplied by the ja value listed in the package section on page 2 to ind the maximum expected die temperature. this must not be allowed to exceed 150c or performance may be degraded. as an example, if an ltc6102 in the msop package is to be biased at 55v 5v supply with 1ma output current at 80c: p q(max) = i dd(max) ? v + (max) = 39mw p out(max) = i out ? v + (max) = 60mw t rise = ja ? p total(max) t max = t ambient + t rise t max must be < 125c p total(max) 99mw and the max die temp will be 100c if this same circuit must run at 125c, the max die temp will increase to 145c. (note that supply current, and therefore p q , is proportional to temperature. refer to typical performance characteristics section.) note that the dd package has a smaller ja than the msop pack - age, which will substantially reduce the die temperature at similar power levels. the ltc6102hv can be used at voltages up to 105v . this additional voltage requires that more power be dissipated for a given level of current. this will further limit the allowed output current at high ambient temperatures. it is important to note that the ltc6102 has been designed to provide at least 1ma to the output when required, and can deliver more depending on the conditions. care must be taken to limit the maximum output current by proper choice of sense and input resistors and, if input fault conditions are likely, an external clamp. downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 17 6102fe for more information www.linear.com/ltc6102 figure 6. v + powered separately from load supply (v b at ) 6102 f06 ltc6102 r out v out r in v bat load (v + C 2v) to v + r sense v + v C out +in v + Cinf Cins v reg 0.1f C + applications information output filteringthe output voltage, v out , is simply i out ? z out . this makes iltering straightforward. any circuit may be used which generates the required z out to get the desired ilter response. for example, a capacitor in parallel with r out will give a low pass response. this will reduce unwanted noise from the output, and may also be useful as a charge reservoir to keep the output steady while driving a switch - ing circuit such as a mux or adc. this output capacitor in parallel with an output resistor will create a pole in the output response at: f rc db out out ? ?? ? 3 1 2 = useful equations input volt age: v volt ag e se ns e = ir se ns es en se ? g ga in : v v cu rre nt ga in : i i out se ns e out s = r r out in e en se out se ns e tr ansc onduc tan ce: i v = = r r se ns e in 11 r r r r in se ns e out tr ansi mp edance: v i out se ns e = ? i in input sense range the inputs of the ltc6102 can function from v + to (v + C 2v). not only does this allow a wide v sense range, it also allows the input reference to be separate from the positive supply (figure 6). note that the difference between v bat and v + must be no more than the input sense voltage range listed in the electrical characteristics table. monitoring voltages above v + and level translation the ltc6102 may be conigured to monitor voltages that are higher than its supply, provided that the negative terminal of the input voltage is within the input sense range of the ltc6102. figure 7 illustrates a circuit in which the ltc6102 has its supply pin tied to the lower potential terminal of the sense resistor instead of the higher potential terminal. the figure 7. ltc6102 supply current monitored with load Cinf Cins ltc6102 r out v out 6102 f07 r in load v bat r sense v + v C out +in v reg 0.1 f C + operation of the ltc6102 is such that the Cins and Cinf pins will servo to within a few microvolts of +in, which is shorted to v + . since the input sense range of the ltc6102 includes v + , the circuit will operate properly. the voltage across r sense will be held across r in by the ltc6102, causing current v sense /r in to low to r out . in this case, the supply current of the ltc6102 is also monitored, as it lows through r sense . because the voltage across r sense is not restricted to the sense range of the ltc6102 in this circuit, v sense can be large compared to the allowed sense voltage. this facilitates the sensing of very large voltages, provided that r in is chosen so that v sense /r in does not exceed downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 18 6102fe for more information www.linear.com/ltc6102 figure 10. additional resistor r3 protects output during supply reversal applications information 6102 f10 ltc6102 r24.99k d1 r1100 r sense C + v + v C out +in v batt r3 1k Cinf Cins v reg 0.1f l o a d adc the allowed output current. the gain is still controlled by r out /r in , so either gain or attenuation may be applied to the input signal as it is translated to the output. finally, the input may be a voltage source rather than a sense resistor, as shown in figure 8. this circuit allows the translation of a wide variety of input signals across the entire supply range of the ltc6102 with only a tiny offset error while retaining simple gain control set by r out /r in . again, very large voltages may be sensed as long as r in is chosen so that i out does not exceed the allowed output current. for example, v in may be as large as 1v with r in = 1k, or as large as 10v with r in = 10k. for a 10v maximum input and a 5v maximum output, r in = 10k and r out = 5k will allow the ltc6102hv to translate v in to v out with a common mode voltage of up to 100v. for the case where a large input resistor is used, a similar resistor in series with +in will reduce error due to input bias current. figure 8. voltage level-shift circuit figure 9. schottky prevents damage during supply reversal Cinf Cins ltc6102 r out v out 6102 f08 r in v in v cm v + v + v C out +in v reg 0.1f C + v out = v in ? r out r in 6102 f09 ltc6102 r24.99k d1 r1100 v batt r sense v + v C Cinf out Cins +in v reg 0.1f l o a d C + reverse supply currentsome applications may be tested with reverse-polarity supplies due to an expectation of this type of fault during operation. the ltc6102 is not protected internally from external reversal of supply polarity. to prevent damage that may occur during this condition, a schottky diode should be added in series with v C (figure 9). this will limit the reverse current through the ltc6102. note that this diode will limit the low voltage performance of the ltc6102 by effectively reducing the supply voltage to the part by v d . in addition, if the output of the ltc6102 is wired to a device that will effectively short it to high voltage (such as through an esd protection clamp) during a reverse supply condi - tion, the ltc6102s output should be connected through a resistor or schottky diode (figure 10). response time the l tc6102 is designed to exhibit fast response to inputs for the purpose of circuit protection or signal transmission. this response time will be affected by the external circuit in two ways, delay and speed. downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 19 6102fe for more information www.linear.com/ltc6102 applications information if the output current is very low and an input transient occurs, there may be a delay before the output voltage begins changing. this can be reduced by increasing the minimum output current, either by increasing r sense or decreasing r in . the effect of increased output current is illustrated in the step response curves in the typical performance characteristics section of this datasheet. note that the curves are labeled with respect to the initial output currents. the speed is also affected by the external circuit. in this case, if the input changes very quickly, the internal ampli - ier will slew the gate of the internal output fet (figure 1) in order to close the internal loop. this results in current lowing through r in and the internal fet. this current slew rate will be determined by the ampliier and fet charac - teristics as well as the input resistor, r in . using a smaller r in will allow the output current to increase more quickly, decreasing the response time at the output. this will also have the effect of increasing the maximum output current. using a larger r out will also decrease the response time, since v out = i out ? r out . reducing r in and increasing r out will both have the effect of increasing the voltage gain of the circuit. bandwidth for applications that require higher bandwidth from the ltc6102, care must be taken in choosing r in . for a gen - eral-purpose op-amp, the gain-bandwidth product is used to determine the speed at a given gain. gain is determined by external resistors, and the gain-bandwidth product is an intrinsic property of the ampliier. the same is true for the l tc6102, except that the feedback resistance is determined by an internal fet characteristic. the feedback impedance is approximately 1/g m of the internal mosfet. the impedance is reduced as current into Cinf is increased. at 1ma, the impedance of the mosfet is on the order of 10k. r in sets the closed-loop gain of the internal loop as 1/(r in ? g m ). the bandwidth is then limited to gbw ? (r in ? g m ), with a maximum bandwidth of around 2mhz. this is illustrated in the characteristic curves, where gain vs frequency for two input conditions is shown. the exact impedance of the mosfet is dificult to determine, as it is a function of input current, process, and capacitance, and has a very different characteristic for low currents vs high currents. however, it is clear that smaller values of r in and smaller values of i out will generally result in lower closed-loop bandwidth. v sense and r in should be chosen to maximize both i out and closed-loop gain for highest speed. theoretically, maximum bandwidth would be achieved for the case where v in = 10vdc and r in = 10k, giving i out = 1ma and a closed-loop gain near 1. however, this may not be possible in a practical application. note that the mosfet g m is determined by the average or dc value of i out , not the peak value. adding dc current to a small ac input will help increase the bandwidth.v reg bypassing the ltc6102 has an internally regulated supply near v+ for internal bias. it is not intended for use as a supply or bias pin for external circuitry. a 0.1f capacitor should be connected between the v reg and v + pins. this capacitor should be located very near to the ltc6102 for the best performance. in applications which have large supply tran - sients, a 6.8v zener diode may be used in parallel with this bypass capacitor for additional transient suppression. enable pin operation the ltc6102-1 includes an enable pin which can place the part into a low power disable state. the enable pin is a logic input pin referenced to v C and accepts standard ttl logic levels regardless of the v + voltage. when the enable pin is driven high, the part is active. when the enable pin is loating or pulled low, then the part is disabled and draws very little supply current. when driven high, the enable pin draws a few microamps of input bias current. if there is no external logic supply available, the enable pin can be pulled to the v + supply through a large value resistor. the voltage at the enable pin will be clamped by the built-in esd protection structure (which acts like a zener diode). the resistor should be sized so that the current through the resistor is a few milliamps or less to prevent any reduction in long-term reliability. for practi - cal purposes, the current through the resistor should be minimized to save power. the resistor value is limited by the input bias current requirements of the enable downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 20 6102fe for more information www.linear.com/ltc6102 applications information Cinf v reg 0.1f Cins 6102 f11 r in + = r in C C r sense ltc6102-1 r out v out v + load r bias 2.7m r sense v + v C out +in en r in C r in + C + figure 11 figure 12. ltc6102-1 v reg voltage during bypass capacitor discharge when disabled pin. figure 11 shows the ltc6102-1 with a 2.7m pull-up resistor to limit the current to less than 20a with a 60v supply, which is enough to satisfy the input bias current requirement. start-up current the start-up current of the ltc6102 when the part is powered on or enabled (ltc6102-1) consists of three parts: the irst is the current necessary to charge the v reg bypass capacitor, which is nominally 0.1f. since the v reg voltage charges to approximately 4.5v below the v + voltage, this can require a signiicant amount of start-up current. the second source is the active supply current of the ltc6102 ampliier, which is not signiicantly greater during start-up than during normal operation. the third source is the output current of the ltc6102, which upon start-up may temporarily drive the output high. this could cause milliamps of output current (limited mostly by the input resistor r in ) to low into the output resistor and/or the output limiting esd structure in the ltc6102. this is a temporary condition which will cease when the ltc6102 ampliier settles into normal closed-loop operation. when the ltc6102-1 is disabled, the internal ampliier is also shut down, which means that the discharge rate of the 0.1f capacitor is very low. this is signiicant when the ltc6102-1 is disabled to save power, because the recharg - ing of the 0.1f capacitor is a signiicant portion of the overall power consumed in startup. figure 12 shows the discharge rate of the 0.1 f capacitor after the l tc6102-1 is shut down at room temperature. in a system where the ltc6102-1 is disabled for short periods, the start-up power (and therefore the average power) can be reduced since the v reg bypass capacitor is never signiicantly discharged. the time required to charge the v reg capacitor will also be reduced, allowing the ltc6102-1 to start-up more quickly. time (ms) C2 0 enable voltage (v) v reg voltage (v) 0.25 0.75 1.00 1.25 10 2.25 6102 f12 0.50 4 0 12 6 2 14 8 16 1.50 1.75 2.00 7.4 7.5 7.7 7.8 7.9 8.37.6 8.0 8.1 8.2 v reg en t a = 25c v + = 12v downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 21 6102fe for more information www.linear.com/ltc6102 bidirectional current sense circuit with separate charge/discharge output ltc6102 monitors its own supply current typical applications charger C + C + +C +C l o a d v out d = i discharge ? r sense ( ) when i discharge 0 discharging: r out d r in d v out c = i charge ? r sense ( ) when i charge 0 charging: r out c r in c 6102 ta02 v batt r in d 100 ltc6102 r in c 100 r in d 100 ltc6102 v out c r out c 4.99k r out d 4.99k v out d r in c 100 i charge r sense i discharge v + v C out Cins +in v + v C out Cins +in Cinf Cinf v reg 0.1f v reg 0.1f l o a d C + 6102 ta03 r2 4.99k v out r1100 v batt r sense ltc6102 +C v out = 49.9 ? r sense (i load + i supply ) i load i supply v + v C out Cins +in Cinf v reg 0.1f downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 22 6102fe for more information www.linear.com/ltc6102 16-bit resolution unidirectional output into ltc2433 adc intelligent high-side switch with current monitor typical applications to p 6102 ta05 ltc2433-1 ltc6102-1 r out 4.99k r in 100 v out v sense i load 4v to 60v power enable 1f 5v l o a d C + C + v out = ? v sense = 49.9v sense r out r in adc full-scale = 2.5v 2 1 98 7 10 6 3 45 v cc sck ref + ref C gnd in + in C c c f o sdd v + v C en out Cins +in Cinf v reg 0.1f 6102 ta06 l o a d fault off on 1 5 4.99k v o r s 34 47k 2 86 100 100 1% 10f 63v 1f 14v v logic sub85n06-5 v o = 49.9 ? r s ? i l for r s = 5m, v o = 2.5v at i l = 10a (full scale) lt1910 ltc6102 i l v + v C out Cins Cinf +in v reg 0.1f downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 23 6102fe for more information www.linear.com/ltc6102 typical applications input overvoltage protection simple 500v current monitor 6102 ta08 ltc6102 r in 100 v out r out 4.99k l o a d C + v out = ? v sense = 49.9 v sense r out r in m1 and m2 are fqd3p50 tm m1 m2 51vbzx884-c51 bat46 2m v sense r sense i sense + C danger! lethal potentials present ? use caution danger!! high voltage!! v + v C out Cins +in 500v Cinf v reg 0.1f ltc6102 dz: central semiconductor cmz5931b 18v 1.5w zener diode 6102 ta07 r in C 1k 3w v + load r sense C + v + Cinf v C d z out v reg 0.1f Cins +in r out 1k downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 24 6102fe for more information www.linear.com/ltc6102 package description ms8 package 8-lead plastic msop (reference ltc dwg # 05-08-1660 rev f) msop (ms8) 0307 rev f 0.53 0.152 (.021 .006) seating plane note:1. dimensions in millimeter/(inch) 2. drawing not to scale 3. dimension does not include mold flash, protrusions or gate burrs. mold flash, protrusions or gate burrs shall not exceed 0.152mm (.006") per side 4. dimension does not include interlead flash or protrusions. interlead flash or protrusions shall not exceed 0.152mm (.006") per side 5. lead coplanarity (bottom of leads after forming) shall be 0.102mm (.004") max 0.18 (.007) 0.254 (.010) 1.10 (.043) max 0.22 C 0.38 (.009 C .015) typ 0.1016 0.0508 (.004 .002) 0.86 (.034) ref 0.65 (.0256) bsc 0 C 6 typ detail a detail a gauge plane 1 2 3 4 4.90 0.152 (.193 .006) 8 7 6 5 3.00 0.102 (.118 .004) (note 3) 3.00 0.102 (.118 .004) (note 4) 0.52 (.0205) ref 5.23 (.206) min 3.20 C 3.45 (.126 C .136) 0.889 0.127 (.035 .005) recommended solder pad layout 0.42 0.038 (.0165 .0015) typ 0.65 (.0256) bsc dd package 8-lead plastic dfn (3mm 3mm) (reference ltc dwg # 05-08-1698 rev c) 3.00 0.10 (4 sides) note:1. drawing to be made a jedec package outline m0-229 variation of (weed-1) 2. drawing not to scale 3. all dimensions are in millimeters 4. dimensions of exposed pad on bottom of package do not include mold flash. mold flash, if present, shall not exceed 0.15mm on any side 5. exposed pad shall be solder plated 6. shaded area is only a reference for pin 1 location on top and bottom of package 0.40 0.10 bottom viewexposed pad 1.65 0.10 (2 sides) 0.75 0.05 r = 0.125 typ 2.38 0.10 1 4 8 5 pin 1 top mark (note 6) 0.200 ref 0.00 C 0.05 (dd8) dfn 0509 rev c 0.25 0.05 2.38 0.05 recommended solder pad pitch and dimensions apply solder mask to areas that are not soldered 1.65 0.05 (2 sides) 2.10 0.05 0.50bsc 0.70 0.05 3.5 0.05 packageoutline 0.25 0.05 0.50 bsc downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 25 6102fe information furnished by linear technology corporation is believed to be accurate and reliable. however, no responsibility is assumed for its use. linear technology corporation makes no representa - tion that the interconnection of its circuits as described herein will not infringe on existing patent rights. revision history rev date description page number d 8/10 updated graph 21 8 e 6/14 web links added correction to output current absolute maximum ratings, (C1ma, +10ma) instead of (+1ma, C10ma)correction to supply current at v + =60v . speciication does not apply over the full operating temperature range all 24 (revision history begins at rev d) downloaded from: http:///
ltc6102 ltc6102-1/ltc6102hv 26 6102fe for more information www.linear.com/ltc6102 linear technology corporation 1630 mccarthy blvd., milpitas, ca 95035-7417 ? linear technology corporation 2007 lt 0614 rev e ? printed in usa (408) 432-1900 fax : (408) 434-0507 www.linear.com/ltc6102 typical application part number description comments lt ? 1636 rail-to-rail input/output, micropower op amp v cm extends 44v above v ee , 55a supply current, shutdown function lt1637 / lt1638 / lt1639 single/dual/quad, rail-to-rail, micropower op amp v cm extends 44v above v ee , 0.4v/s slew rate, >1mhz bandwidth, <250a supply current per ampliier lt1787 / lt1787hv precision, bidirectional, high side current sense ampliier 2.7v to 60v operation, 75v offset, 60a current draw ltc1921 dual C48v supply and fuse monitor 200v transient protection, drives three optoisolators for status lt1990 high voltage, gain selectable difference ampliier 250v common mode, micropower, pin selectable gain = 1, 10 lt1991 precision, gain selectable difference ampliier 2.7v to 18v, micropower, pin selectable gain = C13 to 14 ltc2050 / ltc2051 / ltc2052 single/dual/quad zero-drift op amp 3v offset, 30nv/c drift, input extends down to v C ltc4150 coulomb counter/battery gas gauge indicates charge quantity and polarity lt6100 gain-selectable high side current sense ampliier 4.1v to 48v operation, pin-selectable gain: 10, 12.5, 20, 25, 40, 50v/v ltc6101 / ltc6101hv high voltage high side current sense ampliier in sot-23 4v to 60v/5v to 100v operation, external resistor set gain ltc6103 dual high side precision current sense ampliier 4v to 60v, gain conigurable, 8-pin msop ltc6104 bidirectional high side precision current sense ampliier 4v to 60v, gain conigurable, 8-pin msop lt6105 precision rail-to-rail input current sense ampliier input v cm extends 44v above and 0.3v below v C , 2.85v to 36v operation lt6106 low cost, high side precision current sense ampliier 2.7v to 36v, gain conigurable, sot23 lt6107 high temperature high side current sense ampliier in sot-23 2.7v to 36v, fully tested at C55c and 150c remote current sense with simple noise filter related parts ltc6102 6102 ta09 r in C v + load r sense C + v + Cinf v C out long wire v reg 0.1f tie as close to r in as possible Cins +in r out adc f c = 1 2 ? ? r out ? c out remote adc c out downloaded from: http:///

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